Fully differential input buffer with wide signal swing range

ABSTRACT

An input buffer for use in a differential operational amplifier is disclosed that regulates current through a main input differential pair while preventing output distortion and allowing high linearity. The input buffer includes a main input transistor pair that receives a voltage input, a tail current source, and a squeezable tail current source circuit including a single-ended self-biased folded feedback loop. These are configured such that current through the main input transistor pair is maintained as the voltage input varies. The folded feedback loop includes a folding transistor and a biasing current source that biases the folding transistor. The squeezable tail current source circuit also includes a replica transistor pair, a bias transistor, and a tail transistor pair. The biasing current source and folding transistor isolate the bias transistor and tail transistor pair from a drain voltage of the replica transistor pair, preventing output distortion and allowing high linearity.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.10/761,276, filed Jan. 22, 2004, now pending, which is incorporated byreference herein in its entirety.

BACKGROUND OF THE INVENTION

1. Field of the Invention

This invention relates generally to processors with an analog-to-digitalconversion interface and a buffer to drive the input. More particularly,this invention relates to differential input buffers, such as used inprogrammable gain amplifiers of Asymmetric Digital Subscriber Line(ADSL) receivers.

2. Related Art

The Asymmetric Digital Subscriber Line (ADSL) is one of the newtechnologies used for high-speed Internet access. Data rates up to 9Mb/s are currently available in the standard ADSL offering. An ADSLtransmission system is specified in a frequency-division multiplexedscheme, with the downstream (i.e., central office to customer) utilizinga frequency range of approximately 160 kHz to 1.104 MHz and upstream(i.e., customer to central office) utilizing a frequency range ofapproximately 30 kHz to 138 kHz. In each frequency domain, thefrequencies are divided into data bins with 4 kHz frequency spacing. Fora discrete multi-tone system such as an ADSL system, the data rate isdirectly proportional to the signal-to-noise-distortion ratio (SNDR)available at the receive bins. The data rate increases with an increasein SNDR. High SNDR is achieved with large signal and low harmonicdistortion and low noise.

A single ADSL chip integrates many digital circuits with sensitivefront-end analog circuitry. An ADSL receiver front-end consists of aprogrammable gain amplifier and a unit-gain input buffer for backendanalog-to-digital conversion (ADC). Because the system is typicallymanufactured in a digital process, the supply voltage is scaled with theshrinking transistor geometry. For example, a 0.251 μm process uses asupply voltage of 2.5 volts while a 0.13 μm process can tolerate asupply voltage of only 1.2 volts. When a supply voltage is reduced, thesignal swing that the unit-gain input buffer can handle is limited dueto reduced headroom. This limitation causes a reduction in SNDR.

It is therefore crucial to maximize the range of the signal swing thatthe receiver front-end circuit can process while maintaining lowdistortion performance (i.e., high linearity). Typically this is donewith amplifiers that have one or more squeezable tail current sources.Linearity is important because harmonic distortion results in spilloverfrom data bin to data bin that may corrupt the data spectrum. An ADSLsystem requires a high linearity performance in the neighborhood of 100dB. To accomplish this, the squeezable tail current source must also beextremely linear, which requires a slightly different squeezable tailcurrent source design.

What is needed is a fully differential input buffer with a wide signalswing range that allows for high linearity performance independent ofthe input voltage.

SUMMARY OF THE INVENTION

A squeezable tail current source for use in a differential operationalamplifier is disclosed that regulates the current through a main inputdifferential pair while preventing output distortion and allowing highlinearity. According to an embodiment of the present invention, thesqueezable tail current source includes a first transistor pair thatreplicates a main input transistor pair, wherein both the firsttransistor pair and the main input transistor pair receive a commonvoltage input at their respective gates. The squeezable tail currentsource also includes a second transistor pair, a bias transistor, afirst current source, a folding transistor, and a second current sourcethat biases the folding transistor. These components are configured suchthat current through the main input transistor pair is maintained as thevoltage input varies. Current through the second transistor pair and thebias transistor is squeezed as the voltage input is decreased, therebyincreasing a gate voltage of the bias transistor, and thereby causingcurrent through both the first transistor pair and the main inputtransistor pair to remain nearly constant. In addition, the secondcurrent source and the folding transistor isolate the bias transistorand the second transistor pair from a drain voltage of the firsttransistor pair, thereby causing the first transistor pair and the maininput transistor pair to have a common drain bias, which prevents outputdistortion and allows high linearity to be achieved.

In one embodiment of the present invention, the first transistor pair,the second transistor pair, and the bias transistor are NMOStransistors, and the folding transistor is a PMOS transistor. In anotherembodiment of the present invention, the first transistor pair, thesecond transistor pair, and the bias transistor are PMOS transistors,and the folding transistor is an NMOS transistor.

A differential input buffer that includes two main input differentialpairs, and therefore two squeezable tail current sources is alsodisclosed, according to an embodiment of the present invention. Thedifferential input buffer includes first and second main inputtransistor pairs. The differential input buffer further includes a firstreplica transistor pair that replicates the first main input transistorpair, wherein both the first replica transistor pair and first maininput transistor pair receive a first common voltage input at theirrespective gates. The differential input buffer further includes asecond replica transistor pair that replicates the second main inputtransistor pair, wherein both the second replica transistor pair andsecond main input transistor pair receive a second common voltage inputat their respective gates. The differential input buffer furtherincludes first and second tail transistor pairs, first and second biastransistors, first and second current sources, and first and secondfolding transistors. The differential input buffer further includes afirst biasing current source that biases the first folding transistor,and a second biasing current source that biases the second foldingtransistor.

In this differential input buffer embodiment, the first main inputtransistor pair, the first replica transistor pair, the first tailtransistor pair, the first bias transistor, and the first current sourceare configured such that current through the first main input transistorpair is maintained as the first common voltage input to the first maininput pair varies. Similarly, the second main input transistor pair, thesecond replica transistor pair, the second tail transistor pair, thesecond bias transistor, and the second current source are configuredsuch that current through the second main input transistor pair ismaintained as the voltage input to the second main input pair varies. Inembodiments of the present invention, current through a tail transistorpair and its corresponding bias transistor is squeezed as the voltageinput to the corresponding main input pair is decreased. This increasesa gate voltage of the bias transistor and causes current through boththe corresponding replica transistor pair and main transistor pair toremain nearly constant.

In an embodiment of the present invention, the first biasing currentsource and the first folding transistor isolate the first biastransistor and the first tail transistor pair from a drain voltage ofthe first replica transistor pair, thereby causing the first replicatransistor pair and the first main input transistor pair to have acommon drain bias. Similarly, the second biasing current source and thesecond folding transistor isolate the second bias transistor and thesecond tail transistor pair from a drain voltage of the second replicatransistor pair, thereby causing the second replica transistor pair andthe second main input transistor pair to have a common drain bias. Whenthe replica transistor pair and corresponding main input transistor pairhave a common drain bias, output distortion is prevented and highlinearity is achieved.

In one embodiment of the present invention, the first main inputtransistor pair, the second main input transistor pair, the firstreplica transistor pair, the second replica transistor pair, the firsttail transistor pair, the second tail transistor pair, the first biastransistor, and the second bias transistor are NMOS transistors. In thisembodiment, the first folding transistor and the second foldingtransistor are PMOS transistors. In another embodiment of the presentinvention, the first main input transistor pair, the second main inputtransistor pair, the first replica transistor pair, the second replicatransistor pair, the first tail transistor pair, the second tailtransistor pair, the first bias transistor, and the second biastransistor are PMOS transistors. In this embodiment, the first foldingtransistor and the second folding transistor are NMOS transistors.

In an embodiment of the present invention, the differential input bufferfurther includes first and second stages. The first stage includes aninput coupled to drains of the first and second main input transistorpairs and also includes an output. The second stage includes an inputcoupled to the first stage output and also includes an output coupled toan output of the differential input buffer.

A method of regulating current through a main input differential pair ofa differential amplifier circuit, while maintaining high linearity, isalso disclosed. According to an embodiment of the present invention, themethod includes providing a voltage input to the main input differentialpair. The method further includes mirroring a tail current to that ofthe current through the main input differential pair by using asqueezable tail current source that includes a current source, a firsttransistor pair, a bias transistor, and a second transistor pair. Themethod further includes isolating the bias transistor and the firsttransistor pair from a drain voltage of the second transistor pair,thereby causing the second transistor pair and the main input transistorpair to have a common drain bias. The method further includes squeezingthe tail current as the voltage input is decreased, thereby increasing agate voltage of the bias transistor and allowing current through themain input differential pair to remain nearly constant.

BRIEF DESCRIPTION OF THE DRAWINGS/FIGURES

The accompanying drawings, which are incorporated herein and form partof the specification, illustrate the present invention and, togetherwith the description, further serve to explain the principles of theinvention and to enable a person skilled in the pertinent art to makeand use the invention.

FIG. 1 illustrates a conventional differential operational amplifierwith a squeezable tail current source.

FIG. 2 illustrates a portion of an operational amplifier, highlightingan exemplary conventional mirrored tail current source.

FIG. 3 illustrates a portion of the operational amplifier of FIG. 1,highlighting an exemplary conventional squeezable tail current source.

FIG. 4 illustrates a differential operational amplifier including a tailcurrent source that provides high linearity, according to an embodimentof the present invention.

FIG. 5 illustrates a portion of the operational amplifier of FIG. 4,highlighting the tail current source that provides high linearity,according to an embodiment of the present invention.

FIG. 6 depicts a method of regulating current through a main inputdifferential pair while maintaining high linearity, according to anembodiment of the present invention.

The features and advantages of the present invention will become moreapparent from the detailed description set forth below when taken inconjunction with the drawings in which like reference charactersidentify corresponding elements throughout. In the drawings, likereference numbers generally indicate identical, functionally similar,and/or structurally similar elements. The drawing in which an elementfirst appears is indicated by the leftmost digit(s) in the correspondingreference number.

DETAILED DESCRIPTION OF THE INVENTION

While the present invention is described herein with reference toillustrative embodiments for particular applications, it should beunderstood that the invention is not limited thereto. Those skilled inthe art with access to the teachings provided herein will recognizeadditional modifications, applications, and embodiments within the scopethereof and additional fields in which the present invention would be ofsignificant utility.

FIG. 1 illustrates a conventional four-input differential operationalamplifier with squeezable tail current. Differential operationalamplifier 100 has four input terminals represented by transistorsforming main input differential pairs 102 and 104. Differential pair 102has inputs vip′ and vin. Differential pair 104 has inpus vip and vin′.The transistor banks 106 are bias transistors. An output 108 of a firststage 109 of the amplifier is located at the drains of transistor pair110, which feed into an input of a second stage 112 of the amplifier.Ports vop and von are outputs of amplifier 100. Connecting vop to vin′and von to vip′ creates a unit-gain input buffer.

The amplifier circuit 100 includes squeezable tail current sources tohandle a large input swing. The portions of differential amplifier 100represented by box 103 (encompassing transistors 114, 118, and 122) andby box 105 (encompassing transistors 116, 120, and 124) are referred toherein as squeezable tail current sources 103, 105. As can be seen inFIG. 1, main input pair 102 is coupled to squeezable tail current source103 and main input pair 104 is coupled to squeezable tail current source105. The squeezable tail current sources 103, 105 presented in FIG. 1are described in detail below. Although differential amplifier 100includes more than one squeezable tail current source, only onesqueezable tail current source (103) is described for simplicity of thedescription. Both squeezable tail current sources 103, 105 ofdifferential amplifier 100 operate in a similar manner, as will beunderstood by those skilled in the art.

FIG. 2 illustrates a conventional version 200 of a mirrored tail currentsource that is not shown in FIG. 1, but discussed here for explanatorypurposes. The squeezable tail current source 203 operates as follows. Tomirror current bias, a current source 217 and a bias transistor 218 areneeded, and the current is mirrored to transistor pair 214. As the inputsignal (vip′, vin) decreases, the tail current through transistor pair214 is squeezed. The drain voltage (Vds) of transistor pair 214decreases and the current through transistor pair 214 diminishes. Whenthis happens, the common source voltage of main input pair 202decreases, and the current through main input pair 202 decreases. Tocounter this problem, a replica differential pair 122 is used, as shownand described with reference to FIGS. 1 and 3. FIG. 3 illustratessqueezable tail current source 103, which is the squeezable tail currentsource 103 of differential operational amplifier 100 of FIG. 1 thatcorresponds to main input pair 102.

As seen in FIG. 1, the input (vip′, vin) of replica pair 122 is tied tothe same node as the input (vip′, vin) of the main input pair 102,forming a duplicate of main input pair 102. As the input signal (vip′,vin) is decreased, the common source voltage of replica pair 122 isdecreased, just as it is for main input pair 102. In order to maintain aconstant current flowing through bias transistor 118, the gate voltage(Vgs) of bias transistor 118 must increase. With the configuration shownin FIGS. 1 and 3, when the input (vip′, vin) is decreased, the currentthrough bias transistor 118 is squeezed along with the current throughtransistor pair 114. In this way, a self-adjusting loop is formed by theconnection of the gate of bias transistor 118 to the drains of replicapair 122. This loop adjusts the gate voltage (Vgs) of bias transistor118 such that the gate voltage (Vgs) is increased as input (vip′, vin)is decreased. In other words, when input (vip′, vin) decreases, thedrain voltage (Vds) of replica pair 122 increases, which in turnincreases the gate voltage (Vgs) of bias transistor 118. This causes thecurrent through replica pair 122 to remain nearly constant, andtherefore the mirror tail current into the main input pair 102 remainsnearly constant as well, not changing dramatically when the input (vip′,vin) swings up and down.

A problem with tail current source 103, however, is that the drainvoltages (Vds) of main input pair 102 and replica pair 122 are differentfor most of the input signal. As can be seen in FIGS. 1 and 3, the drainof replica pair 122 is tied to the gate of transistor pair 114, but thedrain of main input pair 102 is not. Because of this difference, if theinput (vip′, vin) is squeezed, the bias transistor 118 and transistorpair 114 will not have a common drain bias. The drain voltage of biastransistor 118 is different than the drain voltage of transistor pair114 in this instance. Sub-micron devices have significant channelmodulation effects. Differences in the drain voltage of the tail currentsource result in current variations (i.e., non-linear current) into maininput pair 102 as the input signal (vip′, vin) changes, resulting indistortions. In other words, the drain voltage (Vds) of replica pair 122is fixed by the gate voltage (Vgs) of bias transistor 118. Therefore,differential pairs 102 and 122 operate at different operating points,which causes non-linearity of the tail current entering main input pair102, resulting in distortion in the output (vop, von).

The distortion problem is more severe when the input signal (vip′, vin)is high. For a high input signal, replica pair 122 can enter trioderegion when the gate voltage is higher than its drain voltage by athreshold voltage. As main input pair 102 operates in the saturationregion, the drain voltage of bias transistor 118 and the drain voltageof transistor pair 114 are so different that good linearity (e.g., inthe 100 dB range) is not achievable.

In order to rectify problems with the tail current source 103 describedabove, the feedback loop created from replica pair 122 and biastransistor 118 in FIG. 3 is modified into a single-ended self-biasedfolded feedback loop, as shown in both FIGS. 4 and 5.

FIG. 4 illustrates a differential operational amplifier 400 thatincludes squeezable tail current sources 432, 434 that allow highlinearity, according to an embodiment of the present invention. Theportions of differential amplifier 400 represented by box 432(encompassing transistors 114, 118, 122, and 440) and by box 434(encompassing transistors 116, 120, 124, and 442) are the squeezabletail current sources. As can be seen in FIG. 4, main input pair 102 iscoupled to squeezable tail current source 432 and main input pair 104 iscoupled to squeezable tail current source 434. The squeezable tailcurrent sources 432, 434 presented in FIG. 4 are described in detailbelow. Although differential amplifier 400 includes more than onesqueezable tail current source, only one squeezable tail current source(432) is described for simplicity of the description. Both squeezabletail current sources 432, 434 of differential amplifier 400 operate in asimilar manner, as will be understood by those skilled in the art.

FIG. 5 illustrates, according to an embodiment of the present invention,a single squeezable tail current source 432 as used with main input pair102 of FIG. 400. In comparison, squeezable tail current source 432 issimilar to squeezable tail current source 103, but also includes a PMOStransistor 440 and a current source 444. PMOS transistor 440 is afolding transistor that is biased by current source 444. The feedbackfrom the drain of replica pair 122 enters the source of foldingtransistor 440 rather than the gate of bias transistor 118. In this way,bias transistor 118 and transistor pair 114 are isolated from the drainvoltage of replica pair 122 by folding transistor 440 and current source444. As can be seen in FIGS. 4 and 5, folding transistor 440 is biasedat the same voltage as transistor pair 110 of amplifier 400. As aresult, replica pair 122 and main input pair 102 operate insubstantially the same manner, with a common drain bias. Even with alarge input (vip′, vin), bias transistor 118 and transistor pair 114also operate in the same bias condition (i.e., they have a common drainbias). With this arrangement, the current is duplicated and is notdistorted by the input. Because no tail current distortion is generated,high linearity is readily achieved. The preferred linearity necessaryfor an ADSL system is 90 dB or higher, with a preferred range of 90dB-120 dB. Those skilled in the art will appreciate that the replicainput branch is scaled independently to meet different bandwidthrequirements for settling.

The squeezable tail current source 103 of the present invention is shownin FIGS. 4 and 5 as an NMOS current source with PMOS folding transistor440 and NMOS input pair 102. Alternatively, a squeezable tail currentsource according to the present invention is possible as a complimentaryPMOS current source with an NMOS folding transistor and a PMOS inputpair (not shown).

One advantage of the described invention is that although foldingtransistor 440 was added, there is still only a single-pole feedbackloop. Therefore, there is no compensation issue and no compensationcapacitor is needed for stability.

A method, according to an embodiment of the present invention, ofregulating current through a main input differential pair whilemaintaining high linearity is described in reference to FIG. 6. Method600 begins at step 680 and immediately proceeds to step 682. In step682, a voltage input is provided to a main input differential pair. Forexample, in FIG. 5, the voltage input is depicted as vip′ and vin at thegates of main input pair 102. In step 684, a tail current is mirrored tothat of the current through the main input differential pair 102 byusing a squeezable tail current source as depicted in FIG. 5. Thesqueezable tail current source of FIG. 5 includes a current source(117), a first transistor pair (transistor pair 114), a bias transistor118, and a second transistor pair (replica pair 122) that are used tomirror the current. In step 686, the bias transistor (118) and the firsttransistor pair (transistor pair 114) are isolated from a drain voltageof the second transistor pair (replica pair 122), thereby causing thesecond transistor pair (replica pair 122) and the main input pair 102 tohave a common drain bias. In step 688, the tail current is squeezed asthe voltage input (vip′, vin) is decreased, thereby increasing a gatevoltage of the bias transistor 118 and allowing current through the maininput differential pair 102 to remain nearly constant. The method endsat step 690.

The invention described herein mainly addresses problems that occur whenthere is a low supply and a large swing. Linearity is not a problem whenthe supplied voltage is high. For example, if the supply is 5 volts, andthere is only a 1-volt swing, linearity is not a problem because theswing is relatively small compared to the 5-volt supply, and asqueezable tail current is not needed. A tail current source like theone shown in FIG. 2 is adequate in this example since transistor pair214 does not enter the linear region. However, if the supply is 2.5volts, and there is a 1-volt swing, linearity is a problem because theswing is relatively large compared to the 2.5-volt supply, which resultsin limited headroom for the tail current source to remain in thesaturation region. One advantage of the described invention is that itsoperation is substantially independent of the input level. Whether theinput is low or high, the tail current entering main input pair 102remains nearly constant and no distortion is introduced. In addition, alarge swing is representative of a large signal. If this signal can beenhanced with high linearity maintained, the better thesignal-to-noise-distortion ratio (SNDR). As SNDR is increased, thefaster the data rate that can be achieved.

Conclusion

This disclosure presents a fully differential input buffer with a widesignal swing range that allows for high linearity performance. Whilevarious embodiments of the present invention have been described above,it should be understood that they have been presented by way of exampleonly, and not limitation. It will be understood by those skilled in theart that various changes in form and details can be made therein withoutdeparting from the spirit and scope of the invention as defined in theappended claims. Thus, the breadth and scope of the present inventionshould not be limited by any of the above-described exemplaryembodiments, but should be defined only in accordance with the followingclaims and their equivalents.

1. An input buffer, comprising: a main input transistor pair thatreceives a voltage input; a tail current source; and a squeezable tailcurrent source circuit coupled to the main input transistor pair and tothe tail current source, the squeezable tail current source circuitincluding a single-ended self-biased folded feedback loop, wherein themain input transistor pair, the tail current source, and the squeezabletail current source circuit are configured such that current through themain input transistor pair is maintained as the voltage input varies. 2.The input buffer of claim 1, wherein the folded feedback loop comprises:a folding transistor; and a biasing current source that biases thefolding transistor.
 3. The input buffer of claim 2, wherein thesqueezable tail current source circuit further includes: a replicatransistor pair coupled to the tail current source and the foldingtransistor that replicates the main input transistor pair and receivesthe voltage input; a bias transistor coupled to the replica transistorpair, the folding transistor, and the biasing current source; and a tailtransistor pair coupled to the bias transistor, the folding transistor,and the biasing current source, wherein the biasing current source andthe folding transistor isolate the bias transistor and the tailtransistor pair from a drain voltage of the replica transistor pair. 4.The input buffer of claim 3, wherein current through the tail transistorpair and the bias transistor is squeezed as the voltage input to themain input transistor pair is decreased, thereby increasing a gatevoltage of the bias transistor, and thereby causing current through boththe replica transistor pair and the main input transistor pair to remainnearly constant.
 5. The input buffer of claim 3, wherein an input to thereplica transistor pair is scaled independently to meet differentbandwidth requirements for settling.
 6. The input buffer of claim 3,wherein the main input transistor pair, the replica transistor pair, thetail transistor pair, and the bias transistor are NMOS transistors. 7.The input buffer of claim 3, wherein the main input transistor pair, thereplica transistor pair, the tail transistor pair, and the biastransistor are PMOS transistors.
 8. The input buffer of claim 2, whereinthe folding transistor is an NMOS transistor.
 9. The input buffer ofclaim 2, wherein the folding transistor is a PMOS transistor.
 10. Adifferential input buffer, comprising: a first main input transistorpair that receives a first voltage input; a second main input transistorpair that receives a second voltage input; a first tail current source;a second tail current source; a first squeezable tail current sourcecircuit coupled to the first main input transistor pair and to the firsttail current source, the first squeezable tail current source circuitincluding a first single-ended self-biased folded feedback loop; asecond squeezable tail current source circuit coupled to the second maininput transistor pair and to the second tail current source, the secondsqueezable tail current source circuit including a second single-endedself-biased folded feedback loop, wherein the first main inputtransistor pair, the first tail current source, and the first squeezabletail current source circuit are configured such that current through thefirst main input transistor pair is maintained as the first voltageinput varies; and wherein the second main input transistor pair, thesecond tail current source, and the second squeezable tail currentsource circuit are configured such that current through the second maininput transistor pair is maintained as the second voltage input varies.11. The differential input buffer of claim 10, wherein the first foldedfeedback loop comprises: a first folding transistor; and a first biasingcurrent source that biases the first folding transistor.
 12. Thedifferential input buffer of claim 11, wherein the first squeezable tailcurrent source circuit further includes: a replica transistor paircoupled to the first tail current source and the first foldingtransistor that replicates the first main input transistor pair andreceives the first voltage input; a bias transistor coupled to thereplica transistor pair, the first folding transistor, and the firstbiasing current source; and a tail transistor pair coupled to the biastransistor, the first folding transistor, and the first biasing currentsource, wherein the first biasing current source and the first foldingtransistor isolate the bias transistor and the tail transistor pair froma drain voltage of the replica transistor pair.
 13. The differentialinput buffer of claim 12, wherein current through the tail transistorpair and the bias transistor is squeezed as the first voltage input tothe first main input transistor pair is decreased, thereby increasing agate voltage of the bias transistor, and thereby causing current throughboth the replica transistor pair and the first main input transistorpair to remain nearly constant.
 14. The differential input buffer ofclaim 12, wherein the first main input transistor pair, the replicatransistor pair, the tail transistor pair, and the bias transistor areNMOS transistors.
 15. The differential input buffer of claim 12, whereinthe first main input transistor pair, the replica transistor pair, thetail transistor pair, and the bias transistor are PMOS transistors. 16.The differential input buffer of claim 11, wherein the first foldingtransistor is an NMOS transistor.
 17. The differential input buffer ofclaim 11, wherein the first folding transistor is a PMOS transistor. 18.The differential input buffer of claim 10, wherein the second foldedfeedback loop comprises: a second folding transistor; and a secondbiasing current source that biases the second folding transistor. 19.The differential input buffer of claim 18, wherein the second squeezabletail current source circuit further includes: a replica transistor paircoupled to the second tail current source and the second foldingtransistor that replicates the second main input transistor pair andreceives the second voltage input; a bias transistor coupled to thereplica transistor pair, the second folding transistor, and the secondbiasing current source; and a tail transistor pair coupled to the biastransistor, the second folding transistor, and the second biasingcurrent source, wherein the second biasing current source and the secondfolding transistor isolate the bias transistor and the tail transistorpair from a drain voltage of the replica transistor pair.
 20. Thedifferential input buffer of claim 19, wherein current through the tailtransistor pair and the bias transistor is squeezed as the secondvoltage input to the second main input transistor pair is decreased,thereby increasing a gate voltage of the bias transistor, and therebycausing current through both the replica transistor pair and the secondmain input transistor pair to remain nearly constant.
 21. Thedifferential input buffer of claim 19, wherein the second main inputtransistor pair, the replica transistor pair, the tail transistor pair,and the bias transistor are NMOS transistors.
 22. The differential inputbuffer of claim 19, wherein the second main input transistor pair, thereplica transistor pair, the tail transistor pair, and the biastransistor are PMOS transistors.
 23. The differential input buffer ofclaim 18, wherein the second folding transistor is an NMOS transistor.24. The differential input buffer of claim 18, wherein the secondfolding transistor is a PMOS transistor.
 25. The differential inputbuffer of claim 10, further comprising: a first stage having an inputcoupled to the first and second main input transistor pairs and havingan output; a second stage having an input coupled to the first stageoutput and having an output; and an output coupled to the second stageoutput.
 26. A method of maintaining a constant current through a maininput transistor pair of a differential amplifier while maintaining highlinearity, the method comprising: providing a voltage input to the maininput transistor pair; mirroring a tail current to that of the currentthrough the main input transistor pair by using a squeezable tailcurrent source configured to isolate a bias transistor and a firsttransistor pair of the squeezable tail current source from a drainvoltage of a second transistor pair of the squeezable tail currentsource, thereby causing the second transistor pair and the main inputtransistor pair to have a common drain bias; and squeezing the tailcurrent as the voltage input is decreased, thereby increasing a gatevoltage of the bias transistor and allowing current through the maininput differential pair to remain nearly constant.